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ts1108 data sheet ts1108 coulomb counter: bidirectional current sense amplifier with integrator + comparator the ts1108 coulomb counter accurately measures battery depletion while also indicat- ing the battery charging polarity. the battery discharge current is monitored by a current- sense amplifier through an external sense resistor. utilizing an integrator and a compa- rator plus a monoshot, the ts1108 voltage-to-frequency converter provides a series of 90 s output pulses at cout which represents an accumulation of coulombs flowing out of the battery. the charge count frequency is adjustable by the integration resistor and capacitor. applications ? power management systems ? portable/battery-powered systems ? smart chargers key features ? coulomb counting plus charge polarity ? adjustable charge count frequency ? external crystal oscillator not required ? low supply current ? current sense amplifier: 0.68 a ? i vdd : 1.93 a ? high side bidirectional current sense amplifier ? wide csa input common mode range: +2 v to +27 v ? low csa input offset voltage: 150 v(max) ? low gain error: 1%(max) ? two gain options available: ? gain = 20 v/v : ts1108-20 ? gain = 200 v/v : ts1108-200 ? 16-pin tqfn packaging (3 mm x 3 mm) silabs.com | smart. connected. energy-friendly. rev. 1.0
1. ordering information table 1.1. ordering part numbers ordering part number description gain v/v TS1108-20IQT163 coulomb counter: bidirectional current sense amplifier with integrator and comparator 20 ts1108-200 iqt1633 coulomb counter: bidirectional current sense amplifier with integrator and comparator 200 note: adding the suffix t to the part number (e.g. ts1108-200iqt1633t) denotes tape and reel. ts1108 data sheet ordering information silabs.com | smart. connected. energy-friendly. rev. 1.0 | 1
2. system overview 2.1 functional block diagram figure 2.1. ts1108 coulomb counter block diagram ts1108 data sheet system overview silabs.com | smart. connected. energy-friendly. rev. 1.0 | 2
2.2 current sense amplifier + output buffer the internal configuration of the ts1108 bidirectional current-sense amplifier is a variation of the ts1101 bidirectional current-sense amplifier. the ts1108 current-sense amplifier is configured for fully differential input/output operation. referring to the block diagram, the inputs of the ts1108s differential input/output amplifier are connected to rs+ and rsC across an external r sense resistor that is used to measure current. at the non-inverting input of the current-sense amplifier, the applied voltage difference in voltage between rs+ and rsC is i load x r sense . since the rsC terminal is the non-inverting input of the internal op-amp, the current-sense op-amp action drives pmos[1/2] to drive current across r gain[a/b] to equalize voltage at its inputs. thus, since the m1 pmos source is connected to the inverting input of the internal op-amp and since the voltage drop across r gaina is the same as the external v sense , the m1 pmos drain-source current is equal to: i d s ( m 1 ) = v s e n s e r g a i n a i d s ( m 1 ) = i l o ad r s e n s e r g a i n a the drain terminal of the m1 pmos is connected to the transimpedance amplifiers gain resistor, rout, via the inverting terminal. the non-inverting terminal of the transimpedance amplifier is internally connected to vbias, therefore the output voltage of the ts1108 at the out terminal is: v o u t = v b i a s ? i l o a d r s e nse r o u t r g a i n a when the voltage at the rsC terminal is greater than the voltage at the rs+ terminal, the external vsense voltage drop is impressed upon r gainb . the voltage drop across r gainb is then converted into a current by the m2 pmos. the m2 pmos drain-source current is the input current for the nmos current mirror which is matched with a 1-to-1 ratio. the transimpedance amplifier sources the m2 pmos drain-source current for the nmos current mirror. therefore the output voltage of the ts1108 at the out terminal is: v o u t = v b i a s + i load r s e nse r o u t r gainb when m1 is conducting current (v rs+ > v rsC ), the ts1108s internal amplifier holds m2 off. when m2 is conducting current (v rsC > v rs+ ), the internal amplifier holds m1 off. in either case, the disabled pmos does not contribute to the resultant output voltage. the current-sense amplifiers gain accuracy is therefore the ratio match of r out to r gain[a/b] . for each of the two gain options availa- ble, the following table lists the values for r gain[a/b] . table 2.1. internal gain setting resistors (typical values) gain (v/v) r gain[a/b] () r out () part number 20 2 k 40 k ts1108-20 200 200 40 k ts1108-200 the ts1108 allows access to the inverting terminal of the transimpedance amplifier by the filt pin, whereby a series rc filter may be connected to reduce noise at the out terminal. the recommended rc filter is 4 k and 0.47 f connected in series from filt to gnd to suppress the noise. any capacitance at the out terminal should be minimized for stable operation of the buffer. ts1108 data sheet system overview silabs.com | smart. connected. energy-friendly. rev. 1.0 | 3
2.3 sign output the ts1108 sign output indicates the load currents direction. the sign output is a logic high when m1 is conducting current (v rs+ > v rsC ). alternatively, the sign output is a logic low when m2 is conducting current (v rsC > v rs+ ). the sign comparators transfer characteristic is illustrated in figure 1. unlike other current-sense amplifiers that implement an out/sign arrangement, the ts1108 exhibits no dead zone at i load switchover. figure 2.2. ts1108 sign output transfer characteristic 2.4 integrator + comparator the ts1108 coulomb counter function utilizes an integrator and a comparator plus a 90 s monoshot. the csas buffered output is applied to the integrators input. this signal is integrated by the comparator until it reaches a level that trips the comparator. the compa- rators trip level is determined by the voltage applied to the comparators non-inverting terminal, cin+. the monoshot produces a 90 s output pulse at cout and the integrator is reset. therefore, each cout 90 s pulse represents an accumulation of coulombs (please refer to the equations in 2.6 coulomb counter ). the ts1108 integrator works best when the 90 s monoshot represents less than 2% of the total integration period. therefore, the minimum integration time for a full-scale v sense should be limited to 4.7 ms. to guarantee stable operation of the out buffer, an integration capacitance of 0.1 f should be used for integration capacitor, c int . the maximum integration period can be very long, limited by the leakage current and offset. a reset switch is configured internally to discharge the external integration capacitor, c int . to enable the coulomb counting feature, sw_rst should be tied to either gnd or cout, allowing the 90 s monoshot pulse to control the discharge of c int . to close the reset switch and short out c int , sw_rst may be tied high. ts1108s coulomb counting interrupt is provided by the internal comparator with a push-pull output configuration. as shown in the block diagram, the integrators output is applied internally to the non-inverting terminal of the comparator, cin+. therefore the compara- tors output will latch high for 90 s once the integrators output is charged to the voltage supplied to the comparators inverting terminal, cinC. the inverting terminal of the comparator, cinC, must be at a higher potential than the voltage supplied to vbias for proper oper- ation. the capacitive load at cout should be minimized for minimal output delays. 2.5 vref divider the ts1108 provides an internal voltage divider network to set vbias and cinC, eliminating the need for externally setting the required voltages. the vref divider is activated once the voltage applied to vref is 0.9 v or greater. the vref divider connects to vbias and cinC, where the vbias voltage is equal to 50% of vref while the cinC voltage is equal to 90% of vref . the vref divider exhibits a typical total series resistance of 4.6 m from vref to gnd when activated. ts1108 data sheet system overview silabs.com | smart. connected. energy-friendly. rev. 1.0 | 4
2.6 coulomb counter the amount of charge, or coulombs, over time is measured by the integration of current. the ts1108 coulomb counter measures the charge consumed by the load by integrating the voltage output of the current sense amplifier, thereby converting the sensed current at the csas applied input into a measurement of coulombs. the comparators output represents a measurement of coulombs per output pulse. the period of the comparators output pulses is defined by: t c o u t = r i n t c i n t ( v c i n ? ? v v b i a s ) gain v s e n s e since a coulomb is defined as the multiplication of current and time, the quantity of coulombs per comparator output pulse can be de- fined as: o n e c o m p arator output p u l s e = r i n t c i n t ( v c i n ? ? v v b i a s ) g a i n r s e n se c ou lombs the comparators output pulse can also quantify the ampere-hours (ah) of battery charge, as most battery manufacturers specify a bat- terys capacity in ampere-hours. o n e c o m p arator output p u l s e = r i n t c i n t ( v c i n ? ? v v b i a s ) 3600 g a i n r s e n s e a h it should be noted that the sense resistor value, r sense , should not be used to adjust the relationship between coulombs and the ap- plied sense current to the csas input. the integration resistor, r int , and the comparators upper limit voltage, v cinC , should be used to adjust the integration time, and therefore the comparators output period. 2.7 selecting a sense resistor selecting the optimal value for the external r sense is based on the following criteria and for each commentary follows: 1. r sense voltage loss 2. v out swing vs. desired v sense and applied supply voltage at vdd 3. total i load accuracy 4. circuit efficiency and power dissipation 5. r sense kelvin connections 2.7.1 rsense voltage loss for lowest ir power dissipation in r sense , the smallest usable resistor value for r sense should be selected. 2.7.2 vout swing vs. desired vsense and applied supply voltage at vdd although the current sense amplifier draws its power from the voltage at its rs+ and rsC terminals, the signal voltage at the out terminal is provided by a buffer, and is therefore bounded by the buffers output range. as shown in the electrical characteristics table, the csa buffer has a maximum and minimum output voltage of: v o u t ( max ) = v dd (min ) ? 0.2 v v o u t ( min ) = 0.2v therefore, the full-scale sense voltage should be chosen so that the out voltage is neither greater nor less than the maximum and minimum output voltage defined above. to satisfy this requirement, the positive full-scale sense voltage, v sense(pos_max) , should be chosen so that: v s e n s e ( p o s _ max ) < vbias ? v o u t ( min ) g a i n likewise, the negative full-scale sense voltage, v sense(neg_min) , should be chosen so that: v s e n s e ( n eg _ min ) < v o u t ( max ) ? v bias g ain for best performance, r sense should be chosen so that the full-scale v sense is less than 75 mv. ts1108 data sheet system overview silabs.com | smart. connected. energy-friendly. rev. 1.0 | 5
2.7.3 total load current accuracy in the ts1108s linear region where v out(min) < v out < v out(max) , there are two specifications related to the circuits accuracy: a) the ts1108 csas input offset voltage (v os(max) = 150 v), b) the ts1108 csas gain error (ge (max) = 1%). an expression for the ts1108s total error is given by: v o u t = v b i as ? g a i n ( 1 g e ) v s e n s e ( ga i n v o s ) a large value for r sense permits the use of smaller load currents to be measured more accurately because the effects of offset voltag- es are less significant when compared to larger v sense voltages. due care though should be exercised as previously mentioned with large values of r sense . 2.7.4 circuit efficiency and power dissipation ir loses in r sense can be large especially at high load currents. it is important to select the smallest, usable r sense value to minimize power dissipation and to keep the physical size of r sense small. if the external r sense is allowed to dissipate significant power, then its inherent temperature coefficient may alter its design center value, thereby reducing load current measurement accuracy. precisely because the ts1108 csas input stage was designed to exhibit a very low input offset voltage, small r sense values can be used to reduce power dissipation and minimize local hot spots on the pcb. 2.7.5 rsense kelvin connections for optimal v sense accuracy in the presence of large load currents, parasitic pcb track resistance should be minimized. kelvin-sense pcb connections between r sense and the ts1108s rs+ and rsC terminals are strongly recommended. the drawing below illustrates the connections between the current-sense amplifier and the current-sense resistor. the pcb layout should be balanced and symmetri- cal to minimize wiring-induced errors. in addition, the pcb layout for r sense should include good thermal management techniques for optimal r sense power dissipation. figure 2.3. making pcb connections to r sense 2.7.6 rsense composition current-shunt resistors are available in metal film, metal strip, and wire-wound constructions. wire-wound current-shunt resistors are constructed with wire spirally wound onto a core. as a result, these types of current shunt resistors exhibit the largest self-inductance. in applications where the load current contains high-frequency transients, metal film or metal strip current sense resistors are recommen- ded. 2.7.7 internal noise filter in power management and motor control applications, current-sense amplifiers are required to measure load currents accurately in the presence of both externally-generated differential and common-mode noise. an example of differential-mode noise that can appear at the inputs of a current-sense amplifier is high-frequency ripple. high-frequency ripple (whether injected into the circuit inductively or ca- pacitively) can produce a differential-mode voltage drop across the external current-shunt resistor, r sense . an example of externally- generated, common-mode noise is the high-frequency output ripple of a switching regulator that can result in common-mode noise in- jection into both inputs of a current-sense amplifier. even though the load current signal bandwidth is dc, the input stage of any current-sense amplifier can rectify unwanted out-of-band noise that can result in an apparent error voltage at its output. against common-mode injection noise, the current-sense amplifiers in- ternal common-mode rejection ratio is 130 db (typ). to counter the effects of externally-injected noise, the ts1108 incorporates a 50 khz (typ), 2nd-order differential low-pass filter as shown in the ts1108s block diagram, thereby eliminating the need for an external low-pass filter, which can generate errors in the offset voltage and the gain error. ts1108 data sheet system overview silabs.com | smart. connected. energy-friendly. rev. 1.0 | 6
2.7.8 pc board layout and power-supply bypassing for optimal circuit performance, the ts1108 should be in very close proximity to the external current-sense resistor and the pcb tracks from r sense to the rs+ and the rsC input terminals of the ts1108 should be short and symmetric. also recommended are surface mount resistors and capacitors, as well as a ground plane. ts1108 data sheet system overview silabs.com | smart. connected. energy-friendly. rev. 1.0 | 7
3. electrical charaviscteristics table 3.1. recommended operating conditions 1 parameter symbol conditions min typ max units system specifications operating voltage range vdd 1.7 5.25 v common-mode input range v cm v rs+ , guaranteed by cmrr 2 27 v note: 1. all devices 100% production tested at ta = +25 c. limits over temperature are guaranteed by design and characterization. table 3.2. dc characteristics 1 parameter symbol conditions min typ max units system specifications no load input supply current i rs+ + i rsC see note 2 0.68 1.2 a i vdd 1.93 2.88 a current sense amplifier common mode rejection ra- tio cmrr 2 v < v rs+ < 27 v 120 130 db input offset voltage 3 v os t a = +25 c 100 150 v C40 c < t a < +85 c 200 v v os hysteresis 4 v hys t a = +25 c 10 v gain g ts1108-20 20 v/v ts1108-200 200 v/v positive gain error 5 ge+ t a = +25 c 0.1 0.6 % C40 c < t a < +85 c 1 % negative gain error 5 geC t a = +25 c 0.6 1 % C40 c < t a < +85 c 1.4 % gain match 5 gm t a = +25 c 0.6 1 % C40 c < t a < +85 c 1.4 % transfer resistance r out from filt to out 28 40 52 k csa buffer input bias current i buffer_bias 0.5 na input referred dc offset v buffer_os 2.5 mv offset drift tcv buffer_os C40 c < t a < +85 c 0.6 v/c input common mode range v buffer_cm 0.2 vdd C 0.2 v csa sign comparator ts1108 data sheet electrical charaviscteristics silabs.com | smart. connected. energy-friendly. rev. 1.0 | 8
parameter symbol conditions min typ max units output low voltage v sign_ol v dd = 1.7 v, i sink = 35 a 0.2 v output high voltage v sign_oh v dd = 1.7 v, i source = 35 a vdd C 0.2 v comparator input bias current i cinC_bias cinC 0.5 na input bias current i cin+_bias cin+ 0.3 na input referred dc offse v c_os 4 mv input common mode range v c_cm 0.4 vdd C 0.4 v cout output range v cout(min,max) i cout = 500 a; vdd = 1.7 v 0.4 vdd C 0.4 v output range v out(min,max) i out = 150 a; vdd = 1.7 v 0.2 vdd C 0.2 v integrator input referred dc offset v int_os 2.5 mv offset drift tcv int_os C40 c < t a < +85 c 0.6 v/ c input common-mode range v int_cm 0.2 vdd C 0.2 v output low voltage i int_ol i cin+(sink) = 150 a; vdd = 1.7 v 0.2 v output high voltage i int_oh i cin+(source) = 150 a; vdd = 1.7 v vdd C 0.2 v vref divider vref activation voltage v ref(min) vref rising edge 0.9 v resistor on vref r vref 4.6 m vbias v vbias vref = 1 v 0.495 0.5 0.505 v cinC v cinC vref = 1 v 0.895 0.9 0.505 v note: 1. rs+ = rsC = 3.6 v; v sense =(v rs+ C v rsC ) = 0 v; vdd = 3 v; vbias = 1.5 v; cin+ = 0.75 v; vref = gnd; clatch = gnd; r fet = 1 m; filt connected to 4 k and 470 nf in series to gnd. t a = t j = C40 c to +85 c unless otherwise noted. typical values are at t a =+25 c. 2. extrapolated to v out = v filt ; i rs+ + i rsC is the total current into the rs+ and the rsC pins. 3. input offset voltage v os is extrapolated from a v out(+) measurement with v sense set to +1 mv and a v out(C) measurement with v sense set to C1 mv; average v os = (v out(C) C v out(+) )/(2 x gain). 4. amplitude of v sense lower or higher than v os required to cause the comparator to switch output states. 5. gain error is calculated by applying two values for v sense and then calculating the error of the actual slope vs. the ideal transfer characteristic. for gain = 20 v/v, the applied v sense for ge is 25 mv and 60 mv. for gain = 200 v/v, the applied v sense for ge is 2.5 mv and 6 mv ts1108 data sheet electrical charaviscteristics silabs.com | smart. connected. energy-friendly. rev. 1.0 | 9
table 3.3. ac characteristics parameter symbol conditions min typ max units csa buffer output settling time t out_s 1% final value, v out = 1.3 v 1.35 msec sign comparator parameters propagation delay t sign_pd v sense = 1 mv 3 msec v sense = 10 mv 0.4 msec reset switch capacitor discharge time t reset c int = 0.1 f; after comparator trigger 60 sec comparator rising propagation delay t c_pdr overdrive = +10 mv, c cout = 15 pf 9 sec comparator hysteresis v c_hys cin+ rising 20 mv monoshot monoshot time t mono 1.7 vdd 5.25 75.5 90 126 sec table 3.4. thermal conditions parameter symbol conditions min typ max units operating temperature range t op -40 +85 c ts1108 data sheet electrical charaviscteristics silabs.com | smart. connected. energy-friendly. rev. 1.0 | 10
table 3.5. absolute maximum limits parameter symbol conditions min typ max units rs+ voltage v rs+ C0.3 27 v rsC voltage v rsC C0.3 27 v supply voltage vdd C0.3 6 v out voltage v out C0.3 6 v sign voltage v sign C0.3 6 v filt voltage v filt C0.3 6 v sw_rst voltage v sw_rst C0.3 6 v cout voltage v cout C0.3 6 v vref voltage v vref C0.3 6 v cin+ voltage v cin+ C0.3 vdd + 0.3 v cinC voltage v cinC C0.3 vdd + 0.3 v intC voltage v intC C0.3 vdd + 0.3 v vbias voltage v vbias C0.3 vdd + 0.3 v rs+ to rsC voltage v rs+ C v rsC 27 v short circuit duration: out to gnd continuous continuous input current (any pin) C20 20 ma junction temperature 150 c storage temperature range C65 150 c lead temperature (soldering, 10 s) 300 c soldering temperature (reflow) 260 c esd tolerance human body model 2000 v machine model 200 v ts1108 data sheet electrical charaviscteristics silabs.com | smart. connected. energy-friendly. rev. 1.0 | 11
for the following graphs, v rs+ = v rsC = 3.6 v; vdd = 3 v; vref = gnd; vbias = 1.5 v, cinC = 2.5 v, sw_rst = cout; r int = 47 k; c int = 0.1 f, and t a = +25 c unless otherwise noted. ts1108 data sheet electrical charaviscteristics silabs.com | smart. connected. energy-friendly. rev. 1.0 | 12
ts1108 data sheet electrical charaviscteristics silabs.com | smart. connected. energy-friendly. rev. 1.0 | 13
ts1108 data sheet electrical charaviscteristics silabs.com | smart. connected. energy-friendly. rev. 1.0 | 14
ts1108 data sheet electrical charaviscteristics silabs.com | smart. connected. energy-friendly. rev. 1.0 | 15
ts1108 data sheet electrical charaviscteristics silabs.com | smart. connected. energy-friendly. rev. 1.0 | 16
4. typical application circuit figure 4.1. ts1108 typical application circuit ts1108 data sheet typical application circuit silabs.com | smart. connected. energy-friendly. rev. 1.0 | 17
5. pin descriptions ts1108 table 5.1. pin descriptions pin label function 1 sign sign output. sign is high for v rs+ > v rsC and low for v rsC > v rs+ . 2 vdd external power supply pin. connect this to the systems vdd supply. 3 vbias bias voltage for csa output. when vref is activated, leave open. 4 gnd ground. connect to analog ground. 5 cinC inverting terminal of comparator. supply a reference voltage for integration limit. cin- voltage must be greater than vbias. if vref is activated, leave open. 6 cin+ integrator output and non-inverting terminal of comparator. connect c int in series from intC. 7 intC inverting terminal of integrator. connect r int in series from out. connect c int in series to cin+. 8 vref voltage reference. to activate, a minimum voltage of 0.9 v is required. to disable voltage divider, connect to analog ground, gnd. 9 out csa buffered output. connect r int in series to intC. 10 filt inverting terminal of csa buffer. connect a series rc filter of 4 k and 0.47 f, otherwise leave open. 11 rs+ external sense resistor power-side connection 12 rsC external sense resistor load-side connection. connect external pfets source. 13 nc no connection. leave open. 14 sw_rst integrator reset switch control. to enable coulomb counting, connect sw_rst to gnd or cout. hold sw_rst high to short cin+ and intC. 15 nc no connection. leave open. 16 cout coulomb comparator counter output. exposed pad epad exposed backside paddle. for best electrical and thermal performance, solder to analog ground. ts1108 data sheet pin descriptions silabs.com | smart. connected. energy-friendly. rev. 1.0 | 18
6. packaging figure 6.1. ts1108 3x3 mm 16-qfn package diagram table 6.1. package dimensions dimension min nom max a 0.70 0.75 0.80 a1 0.00 0.02 0.05 b 0.20 0.25 0.30 c1 1.50 ref c2 0.25 ref d 3.00 bsc d2 1.90 2.00 2.10 e 0.50 bsc e 3.00 bsc e2 1.90 2.00 2.10 l 0.20 0.25 0.30 aaa 0.05 bbb 0.05 ccc 0.05 ddd 0.10 note: 1. all dimensions shown are in millimeters (mm) unless otherwise noted. 2. dimensioning and tolerancing per ansi y14.5m-1994. ts1108 data sheet packaging silabs.com | smart. connected. energy-friendly. rev. 1.0 | 19
7. top marking figure 7.1. top marking table 7.1. top marking explanation mark method laser pin 1 mark: circle = 0.50 mm diameter (lower left corner) font size: 0.50 mm (20 mils) line 1 mark format: product id note: a = 20 gain, b = 200 gain line 2 mark format: tttt C mfg code manufacturing code line 3 mark format: yy = year; ww = work week year and week of assembly ts1108 data sheet top marking silabs.com | smart. connected. energy-friendly. rev. 1.0 | 20
table of contents 1. ordering information ............................1 2. system overview ..............................2 2.1 functional block diagram ..........................2 2.2 current sense amplifier + output buffer .....................3 2.3 sign output ..............................4 2.4 integrator + comparator ..........................4 2.5 vref divider ..............................4 2.6 coulomb counter .............................5 2.7 selecting a sense resistor .........................5 2.7.1 rsense voltage loss ..........................5 2.7.2 vout swing vs. desired vsense and applied supply voltage at vdd ..........5 2.7.3 total load current accuracy ........................6 2.7.4 circuit efficiency and power dissipation ....................6 2.7.5 rsense kelvin connections ........................6 2.7.6 rsense composition ..........................6 2.7.7 internal noise filter ...........................6 2.7.8 pc board layout and power-supply bypassing ..................7 3. electrical charaviscteristics ..........................8 4. typical application circuit ......................... 17 5. pin descriptions ............................. 18 6. packaging ............................... 19 7. top marking ............................... 20 table of contents 21
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